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precision, 20 mhz, cmos, rail-to-rail input/output operational amplifiers ad8615/ad8616/ad8618 rev. e information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ?2004C2008 analog devices, inc. all rights reserved. features low offset voltage: 65 v maximum single-supply operation: 2.7 v to 5.0 v low noise: 8 nv/hz wide bandwidth: >20 mhz slew rate: 12 v/s high output current: 150 ma no phase reversal low input bias current: 1 pa low supply current: 2 ma unity-gain stable applications barcode scanners battery-powered instrumentation multipole filters sensors asic input or output amplifiers audio photodiode amplification general description the ad8615/ad8616/ad8618 are single/dual/quad, rail - to- rail, input and output, single-supply amplifiers featuring very low offset voltage, wide signal bandwidth, and low input voltage and current noise. the parts use a patented trimming technique that achieves superior precision without laser trimming. the ad8615/ad8616/ ad 8618 are fully specified to operate from 2.7 v to 5 v single supplies. the combination of >20 mhz bandwidth, low offset, low noise, and low input bias current makes these amplifiers useful in a wide variety of applications. filters, integrators, photodiode amplifiers, and high impedance sensors all benefit from the combination of performance features. ac applications benefit from the wide bandwidth and low distortion. the ad8615/ad8616/ ad8618 offer the highest output drive capability of the digitrim? family, which is excellent for audio line drivers and other low impedance applications. applications for the parts include portable and low powered instrumentation, audio amplification for portable devices, portable phone headsets, bar code scanners, and multipole filters. the ability to swing rail-to-rail at both the input and output enables designers to buffer cmos adcs, dacs, asics, and other wide output swing devices in single-supply systems. pin configurations ad8615 top view (not to scale) out 1 v? 2 +in 3 v+ ?in 5 4 04648-001 figure 1. 5-lead tsot-23 (uj-5) out a 1 ?in a 2 +in a 3 v? 4 v+ 8 out b 7 ?in b 6 +in b 5 ad8616 top view (not to scale) 04648-002 figure 2. 8-lead msop (rm-8) out a 1 ?in a 2 +in a 3 v? 4 v+ 8 out b 7 ?in b 6 +in b 5 ad8616 top view (not to scale) 04648-003 figure 3. 8-lead soic (r-8) ad8618 top view (not to scale) out a out d ?in a ?in d +in a +in d v+ v? +in b +in c ?in b ?in c 14 8 1 7 out b out c 0 4648-004 figure 4. 14-lead tssop (ru-14) ad8618 top view (not to scale) out a 1 out d 14 ?in a 2 ?in d 13 +in a 3 +in d 12 v+ 4 v? 11 +in b 5 +in c 10 ?in b 6 ?in c 9 out b 7 out c 8 04648-005 figure 5. 14-lead soic (r-14) the ad8615/ad8616/ad8618 are specified over the extended industrial temperature range (?40c to +125c). the ad8615 is available in 5-lead tsot-23 package. the ad8616 is available in 8-lead msop and narrow soic surface-mount packages; the msop version is available in tape and reel only. the ad8618 is available in 14-lead soic and tssop packages.
ad8615/ad8616/ad8618 rev. e | page 2 of 20 table of contents features .............................................................................................. 1 ? applications ....................................................................................... 1 ? general description ......................................................................... 1 ? pin configurations ........................................................................... 1 ? revision history ............................................................................... 2 ? specifications ..................................................................................... 3 ? absolute maximum ratings ............................................................ 5 ? thermal resistance ...................................................................... 5 ? esd caution .................................................................................. 5 ? typical performance characteristics ............................................. 6 ? applications information .............................................................. 11 ? input overvoltage protection ................................................... 11 ? output phase reversal ............................................................... 11 ? driving capacitive loads .......................................................... 11 ? overload recovery time .......................................................... 12 ? d/a conversion ......................................................................... 12 ? low noise applications ............................................................. 12 ? high speed photodiode preamplifier ...................................... 13 ? active filters ............................................................................... 13 ? power dissipation....................................................................... 13 ? power calculations for varying or unknown loads ............. 14 ? outline dimensions ....................................................................... 15 ? ordering guide .......................................................................... 17 ? revision history 9/08rev. d to rev. e changes to general description section ...................................... 1 updated outline dimensions ....................................................... 15 changes to ordering guide .......................................................... 17 5/08rev. c to rev. d changes to layout ............................................................................ 1 changes to figure 38 ...................................................................... 11 changes to figure 44 and figure 45 ............................................. 13 changes to layout .......................................................................... 15 changes to layout .......................................................................... 16 6/05rev. b to rev. c change to table 1 ............................................................................. 3 change to table 2 ............................................................................. 4 change to figure 20 ......................................................................... 8 1/05rev. a to rev. b added ad8615 ................................................................... universal changes to figure 12 ........................................................................ 8 deleted figure 19; renumbered subsequently ............................. 8 changes to figure 20 ........................................................................ 9 changes to figure 29 ...................................................................... 10 changes to figure 31 ...................................................................... 11 deleted figure 34; renumbered subsequently ........................... 11 deleted figure 35; renumbered subsequently ........................... 35 4/04rev. 0 to rev. a added ad8618 ................................................................... universal updated outline dimensions ....................................................... 16 1/04revision 0: initial version
ad8615/ad8616/ad8618 rev. e | page 3 of 20 specifications v s =5 v, v cm = v s /2, t a = 25c, unless otherwise noted. table 1. parameter symbol conditions min typ max unit input characteristics offset voltage, ad8616/ad8618 v os v s = 3.5 v at v cm = 0.5 v and 3.0 v 23 60 v offset voltage, ad8615 23 100 v v cm = 0 v to 5 v 80 500 v ?40c < t a < +125c 800 v offset voltage drift, ad8616/ad8618 ?v os /?t ?40c < t a < +125c 1.5 7 v/c offset voltage drift, ad8615 3 10 v/c input bias current i b 0.2 1 pa ?40c < t a < +85c 50 pa ?40c < t a < +125c 550 pa input offset current i os 0.1 0.5 pa ?40c < t a < +85c 50 pa ?40c < t a < +125c 250 pa input voltage range 0 5 v common-mode rejection ratio cmrr v cm = 0 v to 4.5 v 80 100 db large signal voltage gain a vo r l = 2 k, v o = 0.5 v to 5 v 105 1500 v/mv input capacitance c diff 2.5 pf c cm 6.7 pf output characteristics output voltage high v oh i l = 1 ma 4.98 4.99 v i l = 10 ma 4.88 4.92 v ?40c < t a < +125c 4.7 v output voltage low v ol i l = 1 ma 7.5 15 mv i l = 10 ma 70 100 mv ?40c < t a < +125c 200 mv output current i out 150 ma closed-loop output impedance z out f = 1 mhz, a v = 1 3 power supply power supply rejection ratio psrr v s = 2.7 v to 5.5 v 70 90 db supply current per amplifier i sy v o = 0 v 1.7 2 ma ?40c < t a < +125c 2.5 ma dynamic performance slew rate sr r l = 2 k 12 v/s settling time t s to 0.01% <0.5 s gain bandwidth product gbp 24 mhz phase margin ? m 63 degrees noise performance peak-to-peak noise e n p-p 0.1 hz to 10 hz 2.4 v voltage noise density e n f = 1 khz 10 nv/hz f = 10 khz 7 nv/hz current noise density i n f = 1 khz 0.05 pa/hz channel separation c s f = 10 khz ?115 db f = 100 khz ?110 db
ad8615/ad8616/ad8618 rev. e | page 4 of 20 v s = 2.7 v, v cm = v s /2, t a = 25c, unless otherwise noted. table 2. parameter symbol conditions min typ max unit input characteristics offset voltage, ad8616/ad8618 v os v s = 3.5 v at v cm = 0.5 v and 3.0 v 23 65 v offset voltage, ad8615 23 100 v v cm = 0 v to 2.7 v 80 500 v ?40c < t a < +125c 800 v offset voltage drift, ad8616/ad8618 ?v os /?t ?40c < t a < +125c 1.5 7 v/c offset voltage drift, ad8615 3 10 v/c input bias current i b 0.2 1 pa ?40c < t a < +85c 50 pa ?40c < t a < +125c 550 pa input offset current i os 0.1 0.5 pa ?40c < t a < +85c 50 pa ?40c < t a < +125c 250 pa input voltage range 0 2.7 v common-mode rejection ratio cmrr v cm = 0 v to 2.7 v 80 100 db large signal voltage gain a vo r l = 2 k, v o = 0.5 v to 2.2 v 55 150 v/mv input capacitance c diff 2.5 pf c cm 7.8 pf output characteristics output voltage high v oh i l = 1 ma 2.65 2.68 v ?40c < t a < +125c 2.6 v output voltage low v ol i l = 1 ma 11 25 mv ?40c < t a < +125c 30 mv output current i out 50 ma closed-loop output impedance z out f = 1 mhz, a v = 1 3 power supply power supply rejection ratio psrr v s = 2.7 v to 5.5 v 70 90 db supply current per amplifier i sy v o = 0 v 1.7 2 ma ?40c < t a < +125c 2.5 ma dynamic performance slew rate sr r l = 2 k 12 v/s settling time t s to 0.01% <0.3 s gain bandwidth product gbp 23 mhz phase margin ? m 42 degrees noise performance peak-to-peak noise e n p-p 0.1 hz to 10 hz 2.1 v voltage noise density e n f = 1 khz 10 nv/hz f = 10 khz 7 nv/hz current noise density i n f = 1 khz 0.05 pa/hz channel separation c s f = 10 khz ?115 db f = 100 khz ?110 db
ad8615/ad8616/ad8618 rev. e | page 5 of 20 absolute maximum ratings table 3. parameter rating supply voltage 6 v input voltage gnd to v s differential input voltage 3 v output short-circuit duration to gnd indefinite storage temperature range ?65c to +150c operating temperature range ?40c to +125c lead temperature (soldering, 60 sec) 300c junction temperature 150c stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. thermal resistance ja is specified for the worst-case conditions, that is, ja is specified for a device soldered in a circuit board for surface-mount packages. table 4. package type ja jc unit 5-lead tsot-23 (uj) 207 61 c/w 8-lead msop (rm) 210 45 c/w 8-lead soic (r) 158 43 c/w 14-lead soic (r) 120 36 c/w 14-lead tssop (ru) 180 35 c/w esd caution
ad8615/ad8616/ad8618 rev. e | page 6 of 20 typical performance characteristics 0 200 600 1400 1800 2200 1000 400 1200 1600 2000 800 number of amplifiers ?700 ?500 ?300 ?100 100 300 500 700 offset voltage ( v) v s = 5v t a = 25c v cm = 0v to 5v 0 4648-006 figure 6. input offset voltage distribution 0 2 6 14 18 22 10 4 12 16 20 8 number of amplifiers 024681012 tcv os (v/c) v s = 2.5v t a = ?40c to +125c v cm = 0v 04648-007 figure 7. offset voltage drift distribution ?400 ?500 ?300 ?200 ?100 0 100 200 300 400 500 input offset voltage ( v) 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 common-mode voltage (v) v s = 5v t a = 25c 04648-008 figure 8. input offset voltage vs. common-mode voltage (200 units, five wafer lots including process skews) 0 50 100 150 200 250 300 350 input bias current ( pa) 0 255075100125 temperature (- c) v s = 2.5v 04648-009 figure 9. input bias current vs. temperature sink source 1000 100 10 1 0.1 0.001 0.01 0.1 11 0 i load (ma) v sy ? v out (mv) 100 v s = 5v t a = 25c 0 4648-010 figure 10. output voltage to supply rail vs. load current 0 20 40 60 80 100 120 output s a tur a tion voltage (mv) ?40 ?25 ?10 5 20 35 50 65 80 95 110 125 temperature (c) v s = 5v 1ma load 10ma load 04648-011 figure 11. output saturation voltage vs. temperature
ad8615/ad8616/ad8618 rev. e | page 7 of 20 1m 10m 100 80 60 40 20 0 ?20 ?40 ?60 ?80 ?100 gain (db) 225 180 135 90 45 0 ?45 ?90 ?135 ?180 ?225 phase (degrees) v s = 2.5v t a = 25c ? m = 63 60m frequency (hz) 04648-012 figure 12. open-loop gain and phase vs. frequency 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 output swin g ( v p-p) frequency (hz) 10k 1k 100k 1m 10m v s = 5.0v v in = 4.9v p-p t a = 25c r l = 2k ? a v = 1 0 4648-013 figure 13. closed-loop output voltage swing vs. frequency 0 10 20 30 40 50 60 70 80 90 100 output impedance ( ? ) 1k 10k 100k 1m 10m 100m frequency (hz) a v = 100 a v = 1 a v = 10 v s =2.5v 04648-014 figure 14. output im pedance vs. frequency 0 20 40 60 80 100 120 cmrr (db) frequency (hz) 10k 1k 100k 1m 10m v s =2.5v 04648-015 figure 15. cmrr vs. frequency 0 20 40 60 80 100 120 psrr (db) frequency (hz) 10k 1k 100k 1m 10m v s = 2.5v 04648-016 figure 16. psrr vs. frequency 5 0 10 15 20 25 30 35 40 45 50 small-sign a l overshoot (%) capacitance (pf) 10 100 1000 v s = 5v r l = t a =25c a v = 1 +os ?os 0 4648-017 figure 17. small-signal overshoot vs. load capacitance
ad8615/ad8616/ad8618 rev. e | page 8 of 20 0 0.4 0.8 0.6 0.2 1.2 1.0 supply current per amplifie r ( m a) 1.6 1.4 2.0 1.8 2.4 2.2 ?40 ?25 ?10 5 20 35 50 65 80 95 110 125 temperature (c) v s = 2.7v v s = 5v 0 4648-018 figure 18. supply current vs. temperature 200 0 400 600 800 1000 1200 1400 1600 1800 2000 supply current pe r amplifier (a) 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 supply voltage (v) 04648-019 figure 19. supply current per amplifier vs. supply voltage 1k 100 10 1 10 100 1k 10k 100k frequency (hz) voltage noise density (nv/ hz 0.5 ) v s = 2.5v v s = 1.35v 04648-020 figure 20. voltage noise density vs. frequency voltage (50mv/div) time (1s/div) v s = 5v r l = 10k ? c l = 200pf a v = 1 04648-021 figure 21. small signal transient response volt a g e ( 500mv/div) time (1s/div) v s = 5v r l = 10k ? c l = 200pf a v = 1 0 4648-022 figure 22. large signal transient response thd+n ( % ) 0.0001 0.01 0.001 0.1 frequency (hz) 20 100 1k 20k v s = 2.5v v in = 0.5v rms a v = 1 bw = 22khz r l = 100k ? 04648-023 figure 23. thd + n vs. frequency
ad8615/ad8616/ad8618 rev. e | page 9 of 20 vol t age (2v/div) v s = 2.5v v in = 2v p-p a v = 10 time (200ns/div) 04648-024 figure 24. settling time voltage (1v/div) time (1s/div) v s = 2.7v 04648-025 figure 25. 0.1 hz to 10 hz input voltage noise 0 200 400 600 800 1000 1200 1400 number o f amplifiers ?700 ?500 ?300 ?100 100 300 500 700 offset voltage (v) v s = 2.7v t a = 25 c v cm = 0v to 2.7v 0 4648-026 figure 26. input offset voltage distribution ?400 ?500 ?300 ?200 ?100 0 100 200 300 400 500 input offset voltage (v) 0 0.3 0.6 0.9 1.2 1.5 1.8 2.1 2.4 2.7 common-mode voltage (v) v s = 2.7v t a = 25c 04648-027 figure 27. input offset voltage vs. common-mode voltage (200 units, five wafer lots including process skews) ?400 ?500 ?300 ?200 ?100 0 100 200 300 400 500 input offset voltage (v) 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 common-mode voltage (v) v s = 3.5v t a = 25c 04648-028 figure 28. input offset voltage vs. common-mode voltage (200 units, five wafer lots including process skews) sink source 1000 100 10 1 0.1 0.001 0.01 0.1 1 10 i load (ma) v sy ? v out (mv) v s = 1.35v t a = 25c 04648-029 figure 29. output voltage to supply rail vs. load current
ad8615/ad8616/ad8618 rev. e | page 10 of 20 0 2 4 6 8 10 12 14 16 18 output s a tur a tion voltage (mv) ?40 ?25 ?10 5 20 35 50 65 80 95 110 125 temperature (c) v s = 2.7v v oh @ 1ma load v ol @ 1ma load 0 4648-030 figure 30. output saturation voltage vs. temperature 1m 10m 100 80 60 40 20 0 ?20 ?40 ?60 ?80 ?100 gain (db) 225 180 135 90 45 0 ?45 ?90 ?135 ?180 ?225 phase (degrees) v s = 1.35v t a = 25c ? m = 42 60m frequency (hz) 04648-031 figure 31. open-loop gain and phase vs. frequency 0 0.3 0.6 0.9 1.2 1.5 1.8 2.1 2.4 2.7 output swin g ( v p-p) frequency (hz) 10k 1k 100k 1m 10m v s = 2.7v v in = 2.6v p-p t a = 25c r l = 2k ? a v = 1 04648-032 figure 32. closed-loop output voltage swing vs. frequency 5 0 10 15 20 25 30 35 40 45 50 sm a ll sign a l overshoot (%) capacitance (pf) 10 100 1000 v s = 1.35v r l = t a = 25c a v = 1 +os ?o s 04648-033 figure 33. small signal overshoot vs. load capacitance voltage (50mv/div) time (1s/div) v s = 2.7v r l = 10k ? c l = 200pf a v = 1 0 4648-034 figure 34. small signal transient response voltage (500mv/div) time (1s/div) v s = 2.7v r l = 10k ? c l = 200pf a v = 1 04648-035 figure 35. large signal transient response
ad8615/ad8616/ad8618 rev. e | page 11 of 20 applications information input overvoltage protection the ad8615/ad8616/ad8618 have internal protective circuitry that allows voltages exceeding the supply to be applied at the input. it is recommended, however, not to apply voltages that exceed the supplies by more than 1.5 v at either input of the amplifier. if a higher input voltage is applied, series resistors should be used to limit the current flowing into the inputs. the input current should be limited to <5 ma. the extremely low input bias current allows the use of larger resistors, which allows the user to apply higher voltages at the inputs. the use of these resistors adds thermal noise, which contributes to the overall output voltage noise of the amplifier. for example, a 10 k resistor has less than 13 nv/hz of thermal noise and less than 10 nv of error voltage at room temperature. output phase reversal the ad8615/ad8616/ad8618 are immune to phase inversion, a phenomenon that occurs when the voltage applied at the input of the amplifier exceeds the maximum input common mode. phase reversal can cause permanent damage to the amplifier and can create lock ups in systems with feedback loops. vol t age (2v/div) time (2ms/div) v in v out v s = 2.5v v in = 6v p-p a v = 1 r l = 10k ? 04648-036 figure 36. no phase reversal driving capacitive loads although the ad8615/ad8616/ad8618 are capable of driving capacitive loads of up to 500 pf without oscillating, a large amount of overshoot is present when operating at frequencies above 100 khz. this is especially true when the amplifier is configured in positive unity gain (worst case). when such large capacitive loads are required, the use of external compensation is highly recommended. this reduces the overshoot and minimizes ringing, which in turn improves the frequency response of the ad8615/ad8616/ ad8618. one simple technique for compensation is the snubber, which consists of a simple rc netw ork. with this circuit in place, output swing is maintained and the amplifier is stable at all gains. figure 38 shows the implementation of the snubber, which reduces overshoot by more than 30% and eliminates ringing that can cause instability. using the snubber does not recover the loss of bandwidth incurred from a heavy capacitive load. volt a ge ( 100mv/div) time (2s/div) v s = 2.5v a v = 1 c l = 500pf 0 4648-037 figure 37. driving heavy capacitive loads without compensation v+ 200 ? 500pf 500pf v? v ee v cc 200mv ? + ? 04648-038 figure 38. snubber network volt a ge ( 100mv/div) time (10s/div) v s =2.5v a v = 1 r s = 200 ? c s = 500pf c l = 500pf 04648-039 figure 39. driving heavy capacitive loads using the snubber network
ad8615/ad8616/ad8618 rev. e | page 12 of 20 overload recovery time overload recovery time is the time it takes the output of the amplifier to come out of saturation and recover to its linear region. overload recovery is particularly important in applications where small signals must be amplified in the presence of large transients. figure 40 and figure 41 show the positive and negative overload recovery times of the ad8616. in both cases, the time elapsed before the ad8616 comes out of saturation is less than 1 s. in addition, the symmetry between the positive and negative recovery times allows excellent signal rectification without distortion to the output signal. time (1s/div) v s = 2.5v r l = 10k ? a v = 100 v in = 50mv ?50mv +2.5v 0 v 0 v 0 4648-040 figure 40. positive overload recovery time (1s/div) v s =2.5v r l = 10k ? a v = 100 v in = 50mv +50mv ? 2.5v 0v 0v 04648-041 figure 41. negative overload recovery d/a conversion the ad8616 can be used at the output of high resolution dacs. the low offset voltage, fast slew rate, and fast settling time make the part suitable to buffer voltage output or current output dacs. figure 42 shows an example of the ad8616 at the output of the ad5542 . the ad8616s rail-to-rail output and low distortion help maintain the accuracy needed in data acquisition systems and automated test equipment. ad5542 v out unipolar output agnd dgnd refs 1/2 ad8616 reff v dd serial interface 0.1 f 0.1f 10f 5 v 2.5 v + cs din sclk ldac 0 4648-042 figure 42. buffering dac output low noise applications although the ad8618 typically has less than 8 nv/hz of voltage noise density at 1 khz, it is possible to reduce it further. a simple method is to connect the amplifiers in parallel, as shown in figure 43 . the total noise at the output is divided by the square root of the number of amplifiers. in this case, the total noise is approximately 4 nv/hz at room temperature. the 100 resistor limits the current and provides an effective output resistance of 50 . v? r3 100 ? r1 10 ? v+ v in 3 2 1 r2 1k ? v? r6 100 ? r4 10 ? v+ 3 2 1 r5 1k ? v? r9 100 ? r7 10 ? v+ 3 2 1 r8 1k ? v? r12 100 ? r10 10 ? v+ 3 2 1 r11 1k ? v out 04648-043 figure 43. noise reduction
ad8615/ad8616/ad8618 rev. e | page 13 of 20 high speed photodiode preamplifier the ad8615/ad8616/ad8618 are excellent choices for i-to-v conversions. the very low input bias, low current noise, and high unity-gain bandwidth of the parts make them suitable, especially for high speed photodiode preamplifiers. in high speed photodiode applications, the diode is operated in a photoconductive mode (reverse biased). this lowers the junction capacitance at the expense of an increase in the amount of dark current that flows out of the diode. the total input capacitance, c1, is the sum of the diode and op amp input capacitances. this creates a feedback pole that causes degradation of the phase margin, making the op amp unstable. therefore, it is necessary to use a capacitor in the feedback to compensate for this pole. to get the maximum signal bandwidth, select u f2r 1c 2c = 2 where f u is the unity-gain bandwidth of the amplifier. v? +2.5v v+ ?2.5v r2 c2 c in c d r sh i d ?v bias ? + 04648-044 figure 44. high speed photodiode preamplifier active filters the low input bias current and high unity-gain bandwidth of the ad8616 make it an excellent choice for precision filter design. figure 45 shows the implementation of a second-order, low-pass filter. the butterworth response has a corner frequency of 100 khz and a phase shift of 90. the frequency response is shown in figure 46 . v? v cc v+ v ee 2n f 1nf 1.1k ? 1.1k ? v in 04648-045 figure 45. second-order, low-pass filter ?40 ?30 ?20 ?10 0 10 g a in ( db) 1 0.1 10 100 1k 10k 100k 1m frequency (hz) 0 4648-046 figure 46. second-order butterworth, low-pass filter frequency response power dissipation although the ad8615/ad8616/ad8618 are capable of providing load currents up to 150 ma, the usable output, load current, and drive capability are limited to the maximum power dissipation allowed by the device package. in any application, the absolute maximum junction temperature for the ad8615/ad8616/ad8618 is 150c. this should never be exceeded because the device could suffer premature failure. accurately measuring power dissipation of an integrated circuit is not always a straightforward exercise; figure 47 is a design aid for setting a safe output current drive level or selecting a heat sink for the package options available on the ad8616. power dissip a tion (w) temperature (c) 0 0 0.5 1.0 1.5 20 40 60 80 120 100 140 soic msop 04648-047 figure 47. maximum power dissipation vs. ambient temperature these thermal resistance curves were determined using the ad8616 thermal resistance data for each package and a maximum junction temperature of 150c.
ad8615/ad8616/ad8618 rev. e | page 14 of 20 the following formula can be used to calculate the internal junction temperature of the ad8615/ad8616/ad8618 for any application: t j = p diss ja + t a where: t j = junction temperature p diss = power dissipation ja = package thermal resistance, junction-to-case t a = ambient temperature of the circuit to calculate the power dissipated by the ad8615/ad8616/ ad8618, use the following: p diss = i load ( v s C v out ) where: i load = output load current v s = supply voltage v out = output voltage the quantity within the parentheses is the maximum voltage developed across either output transistor. power calculations for varying or unknown loads often, calculating power dissipated by an integrated circuit to determine if the device is being operated in a safe range is not as simple as it may seem. in many cases, power cannot be directly measured. this may be the result of irregular output waveforms or varying loads. indirect methods of measuring power are required. there are two methods to calculate power dissipated by an integrated circuit. the first is to measure the package temperature and the board temperature. the second is to directly measure the circuits supply current. calculating power by measuring ambient temperature and case temperature the two equations for calculating the junction temperature are t j = t a + p ja where: t j = junction temperature t a = ambient temperature ja = the junction-to-ambient thermal resistance t j = t c + p jc where: t c is case temperature. ja and jc are given in the data sheet. the two equations for calculating p (power) are t a + p ja = t c + p jc p = ( t a ? t c )/( jc ? ja ) once the power is determined, it is necessary to recalculate the junction temperature to ensure that the temperature was not exceeded. the temperature should be measured directly on and near the package but not touching it. measuring the package can be difficult. a very small bimetallic junction glued to the package can be used, or an infrared sensing device can be used, if the spot size is small enough. calculating power by measuring supply current if the supply voltage and current are known, power can be calculated directly. however, the supply current can have a dc component with a pulse directed into a capacitive load, which can make the rms current very difficult to calculate. this difficulty can be overcome by lifting the supply pin and inserting an rms current meter into the circuit. for this method to work, make sure the current is delivered by the supply pin being measured. this is usually a good method in a single-supply system; however, if the system uses dual supplies, both supplies may need to be monitored.
ad8615/ad8616/ad8618 rev. e | page 15 of 20 outline dimensions 091508-a * compliant to jedec standards mo-193-ab with the exception of package height and thickness. 1.60 bsc 2.80 bsc 1.90 bsc 0.95 bsc 0.20 0.08 0.60 0.45 0.30 8 4 0 0.50 0.30 0.10 max * 1.00 max * 0.90 max 0.70 nom 2.90 bsc 54 12 3 seating plane figure 48. 5-lead thin small outline transistor package [tsot] (uj-5) dimensions shown in millimeters compliant to jedec standards mo-187-aa 0.80 0.60 0.40 8 0 4 8 1 5 pin 1 0.65 bsc seating plane 0.38 0.22 1.10 max 3.20 3.00 2.80 coplanarity 0.10 0.23 0.08 3.20 3.00 2.80 5.15 4.90 4.65 0.15 0.00 0.95 0.85 0.75 figure 49. 8-lead mini small outline package [msop] (rm-8) dimensions shown in millimeters
ad8615/ad8616/ad8618 rev. e | page 16 of 20 controlling dimensions are in millimeters; inch dimensions (in parentheses) are rounded-off millimeter equivalents for reference only and are not appropriate for use in design. compliant to jedec standards ms-012-a a 012407-a 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) 0.50 (0.0196) 0.25 (0.0099) 45 8 0 1.75 (0.0688) 1.35 (0.0532) seating plane 0.25 (0.0098) 0.10 (0.0040) 4 1 85 5.00 (0.1968) 4.80 (0.1890) 4.00 (0.1574) 3.80 (0.1497) 1.27 (0.0500) bsc 6.20 (0.2441) 5.80 (0.2284) 0.51 (0.0201) 0.31 (0.0122) coplanarity 0.10 figure 50. 8-lead standard small outline package [soic_n] narrow body (r-8) dimensions shown in millimeters and (inches) controlling dimensions are in millimeters; inch dimensions (in parentheses) are rounded-off millimeter equivalents for reference only and are not appropriate for use in design. compliant to jedec standards ms-012-ab 060606-a 14 8 7 1 6.20 (0.2441) 5.80 (0.2283) 4.00 (0.1575) 3.80 (0.1496) 8.75 (0.3445) 8.55 (0.3366) 1.27 (0.0500) bsc seating plane 0.25 (0.0098) 0.10 (0.0039) 0.51 (0.0201) 0.31 (0.0122) 1.75 (0.0689) 1.35 (0.0531) 0.50 (0.0197) 0.25 (0.0098) 1.27 (0.0500) 0.40 (0.0157) 0.25 (0.0098) 0.17 (0.0067) coplanarity 0.10 8 0 45 figure 51. 14-lead standard small outline package [soic_n] narrow body (r-14) dimensions shown in millimeters and (inches) compliant to jedec standards mo-153-ab-1 061908-a 8 0 4.50 4.40 4.30 14 8 7 1 6.40 bsc pin 1 5.10 5.00 4.90 0.65 bsc 0.15 0.05 0.30 0.19 1.20 max 1.05 1.00 0.80 0.20 0.09 0.75 0.60 0.45 coplanarity 0.10 seating plane figure 52. 14-lead thin shrink small outline package [tssop] (ru-14) dimensions shown in millimeters
ad8615/ad8616/ad8618 rev. e | page 17 of 20 ordering guide model temperature range package desc ription package option branding ad8615aujz-r2 1 C40c to +125c 5-lead tsot-23 uj-5 bka ad8615aujz-reel 1 C40c to +125c 5-lead tsot-23 uj-5 bka ad8615aujz-reel7 1 C40c to +125c 5-lead tsot-23 uj-5 bka AD8616ARM-R2 C40c to +125c 8-lead msop rm-8 bla ad8616arm-reel C40c to +125c 8-lead msop rm-8 bla ad8616armz 1 C40c to +125c 8-lead msop rm-8 a0k ad8616armz-r2 1 C40c to +125c 8-lead msop rm-8 a0k ad8616armz-reel 1 C40c to +125c 8-lead msop rm-8 a0k ad8616ar C40c to +125c 8-lead soic_n r-8 ad8616ar-reel C40c to +125c 8-lead soic_n r-8 ad8616ar-reel7 C40c to +125c 8-lead soic_n r-8 ad8616arz 1 C40c to +125c 8-lead soic_n r-8 ad8616arz-reel 1 C40c to +125c 8-lead soic_n r-8 ad8616arz-reel7 1 C40c to +125c 8-lead soic_n r-8 ad8618ar C40c to +125c 14-lead soic_n r-14 ad8618ar-reel C40c to +125c 14-lead soic_n r-14 ad8618ar-reel7 C40c to +125c 14-lead soic_n r-14 ad8618arz 1 C40c to +125c 14-lead soic_n r-14 ad8618arz-reel 1 C40c to +125c 14-lead soic_n r-14 ad8618arz-reel7 1 C40c to +125c 14-lead soic_n r-14 ad8618aru C40c to +125c 14-lead tssop ru-14 ad8618aru-reel C40c to +125c 14-lead tssop ru-14 ad8618aruz 1 C40c to +125c 14-lead tssop ru-14 ad8618aruz-reel 1 C40c to +125c 14-lead tssop ru-14 1 z = rohs compliant part.
ad8615/ad8616/ad8618 rev. e | page 18 of 20 notes
ad8615/ad8616/ad8618 rev. e | page 19 of 20 notes
ad8615/ad8616/ad8618 rev. e | page 20 of 20 notes ?2004C2008 analog devices, inc. all rights reserved. trademarks and registered trademarks are the prop erty of their respective owners. d04648-0-9/08(e)

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